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information furnished by analog devices is be lieved to be accurate and reliable. however, no responsibility is assumed by analog devices for its use, nor for any infringements of patents or other rights of third parties that may result from its use. no license is granted by implication or other- wise under any patent or patent rights of analog devices. t rademarks and registered trademarks are the property of their respective companies. one technology way, p.o. box 9106, norwood, ma 02062-9106, u.s.a. t el: 781/329-4700 www.analog.com fa x: 781/326-8703 ? 2003 analog devices, inc. all rights reserved. ad626 low cost, single-supply differential ampli er features pin selectable gains of 10 and 100 tr ue single-supply operation single-supply range of +2.4 v to +10 v dual-supply range of 1.2 v to 6 v wide output voltage range of 30 mv to 4.7 v optional low-pass filtering excellent dc performance low input offset voltage: 500 v max large common-mode range: 0 v to +54 v low power: 1.2 mw (v s = +5 v) good cmr of 90 db typ ac performance fast settling time: 24 s (0.01%) includes input protection series resistive inputs (r in = 200 k ) rfi filters included allows 50 v continuous overload applications current sensing interface for pressure transducers, position indicators, strain gages, and other low level signal sources prod uct de scrip tion the ad626 is a low cost, true sin gle-sup ply dif fer en tial am pli er de signed for am pli fy ing and low-pass ltering small dif fer en tial v oltages from sources having a large common-mode voltage. the ad626 can operate from either a single supply of +2.4 v to +10 v, or dual supplies of ?.2 v to ? v. the input common- mode range of this ampli er is equal to 6 (+v s ?1 v) which pro vides a +24 v cmr while operating from a +5 v sup ply. fur ther more, the ad626 features a cmr of 90 db typ. the ampli ers inputs are protected against continuous overload of up to 50 v, and rfi lters are included in the attenuator network. the output range is +0.03 v to +4.9 v using a +5 v sup ply. the ampli er provides a preset gain of 10, but gains be tween 10 and 100 can be easily con g ured with an external re sis tor. fur ther - more, a gain of 100 is available by connecting the g = 100 pin to analog ground. the ad626 also offers low-pass lter capability by connecting a ca pac i tor between the lter pin and analog ground. the ad626a and ad626b operate over the industrial tem per a ture range of ?0? to +85?. the ad626 is available in two 8-lead packages: a plastic mini-dip and soic. 140 0 1m 60 20 1 40 0.1 120 80 100 100k 10k 1k 100 10 frequency ?hz common-mode rejection ?db g = 10, 100 v s = +5v g = 100 v s = 5v g = 10 v s = 5v figure 1. common-mode rejection vs. frequency 25 0 5 15 5 2 10 1 20 4 3 supply voltage ? v input common-mode range ?v v cm for single and dual supplies v cm for dual supplies only figure 2. input common-mode range vs. supply connection diagram 8-lead plastic mini-dip (n) and soic (r) packages 1 2 3 4 8 7 6 5 ad626 1/6 200k ?n analog gnd ? s filter +in g = 100 out +v s 100k g = 2 g = 30 200k rev. d
important links for the ad626 * last content update 09/10/2013 07:55 pm newer alternatives: ad8276 or the ad8278 difference amps for their faster speed, smaller foot print, wider supply voltage range, and lower costs. parametric selection tables find similar products by operating parameters documentation an-282: fundamentals of sampled data systems an-244: a users guide to i.c. instrumentation amplifiers an-245: instrumentation amplifiers solve unusual design problems an-671: reducing rfi rectification errors in in-amp circuits an-589: ways to optimize the performance of a difference amplifier a designers guide to instrumentation amplifiers auto-zero amplifiers high-performance adder uses instrumentation amplifiers input filter prevents instrumentation-amp rf-rectification errors the ad8221 - setting a new industry standard for instrumentation amplifiers applying instrumentation amplifiers effectively: the importance of an input ground return leading inside advertorials: applying instrumentation amplifiers effectivelythe importance of an input ground return design tools, models, drivers & software ad626 spice macro-model ad626a spice macro-model ad626b spice macro-model evaluation kits & symbols & footprints symbols and footprints design collaboration community collaborate online with the adi support team and other designers about select adi products. follow us on twitter: www.twitter.com/adi_news like us on facebook: www.facebook.com/analogdevicesinc design support submit your support request here: linear and data converters embedded processing and dsp telephone our customer interaction centers toll free: americas: 1-800-262-5643 europe: 00800-266-822-82 china: 4006-100-006 india: 1800-419-0108 russia: 8-800-555-45-90 quality and reliability lead(pb)-free data sample & buy ad626 view price & packaging request evaluation board request samples check inventory & purchase find local distributors * this page was dynamically generated by analog devices, inc. and inserted into this data sheet. note: dynamic changes to the content on this page (labeled 'important links') does not constitute a change to the revision number of the product data sheet. this content may be frequently modified. powered by tcpdf (www.tcpdf.org)
?2? ad626?pecifications model ad 626a ad626b p arameter condition min typ max min typ max unit gain gain accuracy total error gain = 10 @ v out 100 mv dc 0.4 1.0 0.2 0.6 % gain = 100 @ v out 100 mv dc 0.1 1.0 0.5 0.6 % over temperature, t a = t min to t max g = 10 50 30 ppm/? g = 100 150 120 ppm/? gain linearity gain = 10 @ v out 100 mv dc 0.014 0.016 0.014 0.016 % gain = 100 @ v out 100 mv dc 0.014 0.02 0.014 0.02 % offset voltage input offset voltage 1.9 2 .5 1.9 2.5 mv vs. temperature t min to t max , g = 10 or 100 2.9 2.9 mv vs. temperature t min to t max , g = 10 or 100 6 6 ?/? vs. supply voltage (psr) +psr 74 8 0 74 80 db ?sr 64 66 64 66 db common-mode rejection r l = 10 k +cmr gain = 10, 100 f = 100 hz, v cm = +24 v 66 90 80 90 db ?mr gain = 10, 100 f = 10 khz, v cm = +6 v 55 64 55 64 db ?mr gain = 10, 100 * f = 100 hz, v cm = ? v 60 85 73 85 db common-mode voltage range +cmv gain = 10 cmr > 85 db +24 +24 v ?mv gain = 10 cmr > 85 db ? ? v input input resistance differential 200 200 k common-mode 100 100 k input voltage range (common-mode) 6 (v s ?l) 6 (v s ?l) v output output voltage swing r l = 10 k positive gain = 10 4.7 4.90 4.7 4.90 v gain = 100 4.7 4.90 4.7 4.90 v negative gain = 10 0.03 0.03 v gain = 100 0.03 0.03 v short circuit current +i sc 12 12 ma noise voltage noise rti gain = 10 f = 0.1 hz?0 hz 2 2 ? p-p gain = 100 f = 0.1 hz?0 hz 2 2 ? p-p gain = 10 f = 1 khz 0.25 0.25 ?/ hz gain = 100 f = 1 khz 0.25 0.25 ?/ hz d ynamic response ? db bandwidth v out = +1 v dc 100 100 khz slew rate, t min to t max gain = 10 0.17 0.22 0.17 0.22 v/? gain = 100 0.1 0.17 0.1 0.17 v/? settling time to 0.01%, 1 v step 24 22 ? power supply operating range t a = t min to t max 2.4 5 12 2.4 5 10 v quiescent current gain = 10 0.16 0.20 0.16 0.20 ma gain = 100 0 .23 0.29 0.23 0.29 ma transistor count number of transistors 46 46 * at temperatures above 25?, ?mv degrades at the rate of 12 mv/?; i.e., @ 25? cmv = ? v, @ 85? cmv = ?.28 v. speci cations subject to change without notice. (@+v s = +5 v and t a = 25 c, un less oth er wise noted.) single supply rev. d
ad626 ?3? model ad 626a ad626b p arameter condition min typ max min typ max unit gain gain accuracy total error gain = 10 r l = 10 k 0.2 0.5 0.1 0.3 % gain = 100 0 .25 1.0 0.15 0.6 % over temperature, t a = t min to t max g = 10 50 30 ppm/? g = 100 100 80 ppm/? gain linearity gain = 10 0.045 0.055 0.045 0.055 % gain = 100 0 .01 0.015 0.01 0.015 % offset voltage input offset voltage 50 50 0 50 250 ? vs. temperature t min to t max , g = 10 or 100 1.0 0.5 mv vs. temperature t min to t max , g = 10 or 100 1.0 0.5 ?/? vs. supply voltage (psr) +psr 74 8 0 74 80 db ?sr 64 66 64 66 db common-mode rejection r l = 10 k +cmr gain = 10, 100 f = 100 hz, v cm = +24 v 66 90 80 90 db ?mr gain = 10, 100 f = 10 khz, v cm = 6 v 55 60 55 60 db common-mode voltage range +cmv gain = 10 cmr > 85 db 26.5 26.5 v ?mv gain = 10 cmr > 85 db 32.5 32.5 v input input resistance differential 200 200 k common-mode 110 110 k input voltage range (common-mode) 6 (v s ?l) 6 (v s ?l) v output output voltage swing r l = 10 k positive gain = 10, 100 4.7 4.90 4.7 4.90 v negative gain = 10 ?.65 ?.1 ?.65 ?.1 v gain = 100 ?.45 ?.8 ?.45 ?.8 v short circuit current +i sc 12 12 ma ? sc 0.5 0.5 ma noise voltage noise rti gain = 10 f = 0.1 hz?0 hz 2 2 ? p-p gain = 100 f = 0.1 hz?0 hz 2 2 ? p-p gain = 10 f = 1 khz 0.25 0.25 ?/ hz gain = 100 f = 1 khz 0.25 0.25 ?/ hz d ynamic response ? db bandwidth v out = +1 v dc 100 100 khz slew rate, t min to t max gain = 10 0.17 0.22 0.17 0.22 v/? gain = 100 0.1 0.17 0.1 0.17 v/? settling time to 0.01%, 1 v step 24 22 ? power supply operating range t a = t min to t max 1.2 5 6 1.2 5 6 v quiescent current gain = 10 1.5 2 1.5 2 ma gain = 100 1 .5 2 1.5 2 ma transistor count number of transistors 46 46 speci cations subject to change without notice. dual supply (@+v s = 5 v and t a = 25 c, un less oth er wise noted.) rev. d
ad626 ?4? caution esd (electrostatic discharge) sensitive device. electrostatic charges as high as 4000 v readily ac cu mu late on the human body and test equipment and can discharge without detection. although the ad626 features proprietary esd pro tec tion circuitry, permanent damage may occur on devices subjected to high energy electrostatic discharges. therefore, proper esd pre cau tions are rec om mend ed to avoid per for mance deg ra da tion or loss of functionality. absolute maximum ratings 1 supply voltage . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . +36 v internal power dissipation 2 p eak input voltage . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . +60 v maximum reversed supply voltage limit . . . . . . . . . . . . . ?4 v output short circuit duration . . . . . . . . . . . . . . . . . . inde nite storage temperature range (n, r) . . . . . . . . . ?5? to +125? operating temperature range ad626a/ad626b . . . . . . . . . . . . . . . . . . . . 40? to +85? lead temperature range (soldering 60 sec) . . . . . . . . . +300? metallization photograph dimensions shown in inches and (mm). notes 1 stresses above those listed under absolute max i mum ratings may cause per ma nent damage to the device. this is a stress rating only; functional operation of the device at these or any other conditions above those indicated in the operational section of this speci cation is not implied. exposure to ab so lute maximum rating con di tions for extended periods may affect device re li abil i ty. 2 8-lead plastic package: ja = 100?/w; jc = 50?/w. 8-lead soic package: ja = 155?/w; jc = 40?/w. ordering guide temperature package package model range description option ad626an 40? to +85? plastic dip n-8 ad626ar ?0? to +85? small outline ic r-8 ad626bn ?0? to +85? plastic dip n-8 ad626ar-reel ?0? to +85? 13" tape and reel ad626ar-reel7 ?0? to +85? 7" tape and reel rev. d
?5? t ypical performance characteristics?d626 25 0 5 15 5 2 10 1 20 4 3 supply voltage ? v input common-mode range ?v v cm for single and dual supplies v cm for dual supplies only tpc 1. input common-mode range vs. supply supply voltage ?v positive output voltage swing ?v 5 0 5 3 1 1 2 0 4 4 3 2 dual supply only single and dual supply t a = 25 c tpc 2. positive output voltage swing vs. supply voltage supply voltage ?v negative output voltage swing ?v ? 0 5 ? ? 1 ? 0 ? 4 3 2 dual supply only t a = 25 c tpc 3. negative output voltage swing vs. supply voltage 6 1 ? 10 100 10k 1k 4 0 2 3 5 load resistance ? positive output voltage ?v v s = 5v gain = 10, 100 tpc 4. positive output voltage swing vs. resistive load ? ? 1 100 1k 100k 10k ? 0 ? ? ? load resistance ? negative output voltage ?v gain = 10 gain = 100 tpc 5. negative output voltage swing vs. resistive load 30 0 0 5 20 10 14 3 2 warm-up time ?minutes change in offset voltage ? v tpc 6. change in input offset voltage vs. warm-up time rev. d
ad626 ?6? 1000 100 0 10 100 1m 100k 10k 1k 10 frequency ?hz closed-loop gain gain = 100 gain = 10 v s = 5v dual supply v s = +5v single supply v s = 5v dual supply tpc 7. closed-loop gain vs. frequency 140 0 1m 60 20 1 40 0.1 120 80 100 100k 10k 1k 100 10 frequency ?hz common-mode rejection ?db g = 10, 100 v s = +5 g = 100 v s = 5 g = 10 v s = 5 tpc 8. common-mode rejection vs. frequency 100 65 25 80 70 0 75 ? 95 85 90 20 15 10 5 input common-mode voltage ?v common-mode rejection ?db g = 10, 100 v s = +5 tpc 9. common-mode rejection vs. input common- mode voltage for single-supply operation 100 65 30 80 70 22 75 20 95 85 90 28 26 24 input common-mode voltage ?v common-mode rejection ?db v s = 5 tpc 10. common-mode rejection vs. input common- mode voltage for dual-supply operation 100 60 080 90 70 20 80 40 60 input source resistance mismatch ? common-mode rejection ?db g = 10, 100 tpc 11. common-mode rejection vs. input source r esistance mismatch 0.6 10 100 1k 0.5 0.4 0.3 0.2 0.1 source resistance mismatch ? additional gain error ?% 0.7 0.0 total gain error = gain accuracy (from spec table) + additional gain error curve applies to all supply voltages and gains between 10 and 100 tpc 12. additional gain error vs. source r esistance mismatch rev. d
ad626 ?7? 0.16 0.12 1 5 0.15 0.13 2 0.14 3 4 supply voltage ?v quiescent current ?ma g = 10 tpc 13. quiescent supply current vs. supply voltage for single-supply operation 2.0 0 1 5 1.5 0.5 2 1.0 3 4 supply voltage ?v quiescent current ?ma tpc 14. quiescent supply current vs. supply voltage for dual-supply operation 10 1.0 0.01 11 0 100k 10k 1k 100 0.1 voltage nsd ? v/ hz frequency ?hz gain = 10, 100 v s = 5v dual supply tpc 15. noise voltage spectral density vs. frequency 5 seconds per horizontal division 2 v per vertical division tpc 16. 0.1 hz to 10 hz rti voltage noise. v s = ? v, gain = 100 100 80 0 110 1m 100k 10k 1k 100 60 40 20 value of resistor r g ? closed-loop gain for v s = 5v and +5v tpc 17. closed-loop gain vs. r g 20 1m 60 40 1 0.1 100 80 120 140 100k 10k 1k 100 10 frequency ?hz power supply rejection ?db all curves for gains of 10 or 100 single and dual ?srr dual + psrr dual + psrr single + psrr tpc 18. power supply rejection vs. frequency rev. d
ad626 ?8? 10 90 100 0% tpc 19. large signal pulse response. v s = ? v, g = 10 10 90 100 0% tpc 20. large signal pulse response. v s = ? v, g = 100 10 90 100 0% tpc 21. large signal pulse response. v s = +5 v, g = 10 10 90 100 0% tpc 22. large signal pulse response. v s = +5 v, g = 100 10 90 100 0% tpc 23. settling time. v s = ? v, g = 10 10 90 100 0% 500mv tpc 24. settling time. v s = ? v, g = 100 rev. d
ad626 ?9? 10 90 100 0% tpc 25. settling time. v s = +5 v, g = 10 ad626 c1 5pf +in ?n r1 200k r2 200k r3 41k c2 5pf r4 41k r5 4.2k r11 10k r6 500 r7 500 r8 10k r10 10k r14 555 gnd gain = 100 r13 10k r15 10k r17 95k r9 10k r12 100k filter out +v s a1 a2 ? s figure 4. simpli ed schematic 10 90 100 0% tpc 26. settling time. v s = +5 v, g = 100 10k 10k 10k input 20v p? 1k +v s ad626 ? s error out 2k figure 3. settling time test circuit theory of operation the ad626 is a differential ampli er con sist ing of a precision bal anced attenuator, a very low drift preampli er (a1), and an out put buffer ampli er (a2). it has been designed so that small differential signals can be accurately am pli ed and ltered in the presence of large common -mode voltages (v cm ), without the use of any other active components. figure 4 shows the main elements of the ad626. the signal in puts at pins 1 and 8 are rs t applied to dual resistive at ten u a tors r1 through r4 whose purpose is to reduce the peak com mon-mode v oltage at the input to the preampli er? feed back stage based on the very low drift op amp a1. this allows the dif feren tial input voltage to be accurately ampli ed in the pres ence of large common-mode volt ag es six times greater than that which can be tol er at ed by the actual input to a1. as a re sult, the in put cmr ex tends to six times the quantity (v s ?1 v). the over all common - mode error is min i mized by precise laser-trimming of r3 and r4, thus giving the ad626 a common-mode re jec tion ra tio (cmrr) of at least 10,000:1 (80 db). to minimize the effect of spurious rf signals at the inputs due to recti cation at the input to a1, small lter capacitors c1 and c2 are included. the output of a1 is connected to the in put of a2 via a 100 k (r12) resistor to facilitate the low-pass ltering of the sig nal of in ter est (see low-pass filtering section). the 200 k input impedance of the ad626 requires that the source re sis tance driving this ampli er be low in val ue (<1 k )?his is rev. d
ad626 ?10? necessary to min i mize gain error. also, any mis match be tween the total source re sis tance at each input will af fect gain ac cu ra cy and common -mode rejection (cmr). for ex am ple: when operating at a gain of 10, an 80 mismatch in the source re sis tance between the inputs will degrade cmr to 68 db. the output buffer, a2, operates at a gain of 2 or 20, thus setting the overall, precalibrated gain of the ad626 (with no ex ter nal com po nents) at 10 or 100. the gain is set by the feedback net work around ampli er a2. the output of ampli er a2 relies on a 10 k resistor to ? s for ?ull-down. for single-supply operation, (? s = ?nd?, a2 can drive a 10 k ground ref er enced load to at least +4.7 v. the min i mum, nominally ?ero, output voltage will be 30 mv. for dual-supply op er a tion (? v), the positive output voltage swing will be the same as for a single supply. the negative swing will be to ?.5 v, at g = 100, limited by the ratio: v rr rrr s + ++ 15 14 13 14 15 the negative range can be extended to ?.3 v (g = 100) and ? v (g = 10) by add ing an external 10 k pull-down from the out put to ? s . this will add 0.5 ma to the ad626s qui es cent cur rent, bringing the total to 2 ma. the ad626s 100 khz bandwidth at g = 10 and 100 (a 10 mhz gain bandwidth) is much higher than can be obtained with low power op amps in discrete dif fer en tial ampli er circuits. fur ther - more, the ad626 is stable driving capacitive loads up to 50 pf (g10) or 200 pf (g100). capacitive load drive can be increased to 200 pf (g10) by connecting a 100 resistor in series with the ad626s output and the load. adjusting the gain of the ad626 the ad626 is easily con gured for gains of 10 or 100. figure 5 shows that for a gain of 10, pin 7 is simply left un con nect ed; simi- larly, for a gain of 100, pin 7 is grounded, as shown in fig ure 6. gains between 10 and 100 are easily set by connecting a vari able resistance between pin 7 and analog gnd, as shown in fig ure 7. because the on-chip resistors have an absolute tol er ance of ?0% (although they are ratio matched to within 0.1%), at least a 20% adjustment range must be provided. the values shown in the table in figure 7 provide a good trade-off be tween gain set range and resolution, for gains from 11 to 90. 0.1 f output +v s not connected +input ?nput 0.1 f 1 2 3 4 8 7 6 5 ?n +in g = 10 out ad626 200k 200k 100k g = 2 analog gnd ? s filter 1/6 +v s ? s g = 30 figure 5. ad626 con gured for a gain of 10 0.1 f output +input ?nput 0.1 f 1 2 3 4 8 7 6 5 ?n +in g = 100 out ad626 200k 200k 100k analog gnd ? s filter 1/6 +v s +v s ? s g = 30 g = 2 figure 6. ad626 con gured for a gain of 100 r g r h cf filter (optional) output +v s +input ?nput 0.1 f 1 2 3 4 8 7 6 5 ?n +in g = 100 out ad626 200k 200k 100k analog gnd ? s filter 1/6 +v s corner frequency of filter = 1 2 cf (100k ) gain range r g ( ) r h ( ) 11 ?20 20 ?40 40 ?80 80 ?100 100k 10k 1k 100 4.99k 802 80 2 resistor values for gain adjustment 0.1 f ? s g = 2 g = 30 figure 7. recommended circuit for gain adjustment single-pole low-pass filtering a low-pass lter can be easily implemented by using the fea tures provided by the ad626. by simply connecting a capacitor between pin 4 and ground, a single-pole low-pass lter is created, as shown in figure 8. cf corner frequency of filter = 1 2 cf (100k ) output +10v +input ?nput 0.1 f 1 2 3 4 8 7 6 5 ?n +in g = 100 out ad626 200k 200k 100k analog gnd ? s filter 1/6 +v s g = 2 g = 30 figure 8. a one-pole low-pass filter circuit which operates from a single +10 v supply rev. d
ad626 ?11? current sensor interface a typical current sensing application, making use of the large common-mode range of the ad626, is shown in figure 9. the cur rent being measured is sensed across resistor r s . the value of r s should be less than 1 k and should be selected so that the av erage differential voltage across this resistor is typically 100 mv. to produce a full-scale output of +4 v, a gain of 40 is used adjust- able by ?0% to absorb the tolerance in the sense re sis tor. note that there is suf cient headroom to allow at least a 10% over range (to +4.4 v). r g r h cf optional low-pass filter output +v s current in c urrent out 0.1 f 1 2 3 4 8 7 6 5 ?n +in g = 100 out ad626 200k 200k 100k analog gnd ? s filter 1/6 +v s 0.1 f ? s r s current sensor g = 2 g = 30 figure 9. current sensor interface bridge application figure 10 shows the ad626 in a typical bridge application. here, the ad626 is set to operate at a gain of 100, using dual-sup ply v oltages and offering the option of low-pass ltering. cf optional low-pass filter output +5v 0.1 f 1 2 3 4 8 7 6 5 ?n +in g = 100 out ad626 200k 200k 100k analog gnd ? s filter 1/6 +v s 0.1 f ?v +v s g = 30 g = 2 figure 10. a typical bridge application rev. d
c00781?0?1/03(d) printed in u.s.a. ?12? ad626 revision history location page 1/03?data sheet changed from rev. c to rev. d. renumbered figures and tpcs . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . universal edits to figure 1 . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 1 edits to specifications, output . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 3 edit to ordering guide . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 4 update to standard caution/esd warning note and diagram . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 4 edits to tpc 8 . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 6 updated outline dimensions . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 12 outline dimensions 8-lead standard small outline package [soic] narrow body (r-8) dimensions shown in millimeters and (inches) 0.25 (0.0098) 0.19 (0.0075) 1.27 (0.0500) 0.41 (0.0160) 0.50 (0.0196) 0.25 (0.0099) 45 8 0 1.75 (0.0688) 1.35 (0.0532) seating plane 0.25 (0.0098) 0.10 (0.0040) 85 4 1 5.00 (0.1968) 4.80 (0.1890) 4.00 (0.1574) 3.80 (0.1497) 1.27 (0.0500) bsc 6.20 (0.2440) 5.80 (0.2284) 0.51 (0.0201) 0.33 (0.0130) coplanarity 0.10 compliant to jedec standards ms-012aa controlling dimensions are in millimeters; inch dimensions (in parentheses) are rounded-off millimeter equivalents for reference only and are not appropriate for use in design 8-lead plastic dual-in line package [pdip] (n-8) dimensions shown in inches and (millimeters) seating plane 0.015 (0.38) min 0.180 (4.57) max 0.150 (3.81) 0.130 (3.30) 0.110 (2.79) 0.060 (1.52) 0.050 (1.27) 0.045 (1.14) 8 1 4 5 0.295 (7.49) 0.285 (7.24) 0.275 (6.98) 0.100 (2.54) bsc 0.375 (9.53) 0.365 (9.27) 0.355 (9.02) 0.150 (3.81) 0.135 (3.43) 0.120 (3.05) 0.015 (0.38) 0.010 (0.25) 0.008 (0.20) 0.325 (8.26) 0.310 (7.87) 0.300 (7.62) 0.022 (0.56) 0.018 (0.46) 0.014 (0.36) compliant to jedec standards mo-095aa controlling dimensions are in inches; millimeter dimensions (in parentheses) are rounded-off inch equivalents for reference only and are not appropriate for use in design rev. d

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